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the SL486 is a high gain preamplifier designed to form an interface between an infra-red receiving diode and the digital input of remote control receiving circuits. the device contains two other circuit elements, one to provide a stretched output pulse facility and a voltage regulator to allow operation from a wide range of supplies. features n fast acting agc improves operation in noisy environments n differential inputs reduce noise pick-up and improve stability n gyrator circuit allows operation in environments with high brightness background light levels n output pulse stretcher for use with microprocessor decoders n on-chip regulator allows operation from wide range of power supplies n low noise output 3055-2.2 SL486 infra red remote control preamplifier fig. 2 SL486 block diagram ordering information SL486 na dp SL486 na mp diode cathode gyrator c2 gyrator c1 input v cc (v cci ) 2nd stage decouple 4th stage decouple output v cc (v cco ) agc decouple diode anode 1st stage decouple input v ee (v eei ) output v ee (v eeo ) regulator input (v regin ) stretch output stretch input output SL486 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 dp16 mp16 1 10v wrt v eei 1 10v wrt v eeo 2 20v wrt v cco 5ma 5ma 0 c to 1 70 c 2 55 c to 1 150 c absolute maximum ratings supply voltage, v cci supply voltage, v cco regulator input voltage, v regin output current stretch output current operating temperature range storage temperature 54k 24k gyrator differential input stage diode cathode diode anode buffer 15k agc peak detector regulator pulse stretch 1 16 14 15 8 12 13 v eei 1st stage decouple agc decouple v eeo regulator input (v regin ) 9 10 11 output stretch input stretch output v cco 4th stage decouple 7 6 2nd stage decouple 5 2 3 gyrator c1 c2 4 v cci v reg * * when regulator is used (see application notes). fig. 1 pin connections - top view (supersedes version in april 1994 consumer ic handbook, hb3120 - 2.0)
2 SL486 electrical characteristics these characteristics are guaranteed over the following conditions (unless otherwise stated): t amb = 1 25 c, v cci = v cco = v cc = 1 45v to 1 70v, v eei = v eeo = v ee = 0v characteristic value min. pin 65 42 1 3i d 85 62 35 40 680 550 24 07 15 08 typ. max. 90 5 1 3i d 10 95 18 65 15 11 23 185 420 v eeo 1 035 v eeo 1 05 units ma ma ma v v v v v na na na db ma (pk) db k w ms %/ c v v v v v (pk) v (pk) conditions supply current (see note 1) low voltage supply wrt v eei &v eeo high voltage supply wrt v regin int. regulated voltage, v reg, wrt v cco | v cci 2 v cco | minimum sensitivity of differential input common mode rejection maximum signal input agc range output and stretch output internal pull-up resistance stretch output pulse width, t p temperature coefficient of r x output low voltage output high voltage stretch output low voltage stretch output high voltage v cci supply rejection 4,7 4 4,7 4,7 4,7 13 4,7 1,16 1,16 1,16 9, 11 11 9 9 11 11 4 35 1 3i d 45 84 59 90 740 1680 30 v cco 2 05 v cco 2 01 note 1. i d = ir diode forward current v cc = 50v, i d = 10 m a v cc = 45v, i d < 15ma v cc = 18v, i d = 10 m a, v regin = 0v v eei = v eeo = v reg (see figs. 4 & 6) v cco 1 v regin = 1 16v t amb = 1 70 c i d = 10 m a i d = 100 m a i d = 05ma capacitance pin 9 to pin 10 (c8 on figs. 4 and 8) = 10nf; 15 v cc where r x = 200k w 6 25% and r x = internal resistance) i sink = 02ma max. i source = 5 m a i sink = 16ma max. i source = 5 m a, output open circuit ripple amplitude at 100hz, v regin = 0v ripple amplitude at 100hz, v eeo and v eei = 0v ? ? t p ? 2 r x c 8 log e ms
3 SL486 inverse to that of the output on pin 9 so must be re-inverted for microprocessor applications. regulator input, v regin (pin 12) the device can be operated with supplies of between 45v and 90v connected between input/output ground (pins 14 and 13) and input and output v cc (pins 4 and 7) as shown in fig. 3. the device can also be operated with supplies in excess of 90v by using the on-chip regulator. in this case connections are made between v cco (pin 7) and the regulator input v regin (pin 12) as shown in fig. 4. a supply voltage of between 90v and 18v will then cause v eeo (pin 13) to be regulated at a level nominally 64v below v cco (pin 7). the regulator will, however, lose control with a potential difference of less than 90v. below this level the voltage on pin 13 will track nominally 15v above the level of pin 12. when the regulator is not used (low voltage operation), pin 12 must be connected to v eeo (pin 13). operating notes - refer to figs. 3 and 4 gyrator c1 (pin 3) if the environment in which the device is operating limits the background light such that the dc compo- nent of the diode current has a maximum of 200 m a, it may be desirable to omit (as in fig. 3) the more bulky and costly 68 m f capacitor (gyrator c1 shown in fig. 4). in this case pin 3 can be left open circuit. the resultant application will then have a characteristic of greatly reduced gain when the ambient light causes the dc current to rise above this threshold. alternatively,the 68 m f capacitor can be replaced by a resistor. the outcome of this is to further reduce the gain in ambient light levels above the 200 m a threshold. below this threshold the overall gain is slightly enhanced as the light level ap- proaches the threshold value. if chosen, this resistance should lie between 10k w and 200k w . noise immunity the stretch output can also be used as a means of improving performance relating to a receiver sys- tem, over and above its main purpose of providing a micro- processor interface. including c8 (fig. 4) causes the output pulses (from pin 9) to be subjected to the stretch input threshold. thus any noise pulses from pin 9 that are below this threshold will not be seen at the stretch output (pin 11). a further improvement can be made, using this stretch input threshold, by including some additional filtering of the output (c10 in fig. 4). this can be adjusted in value (typically 100pf) to reduce some of the noise pulses that otherwise cross the threshold, to a level below the threshold. screening use of screening for the device, and associated components, improves the performance and immunity to externally radiated noise. the screening method used must protect the sensitive front-end of the device; provided that the diode, pin 1-pin 16, c2 (pin 2) and the first stage decoupling (pin 15) are screened, it may be found that for the application considered, the remalning circuitry need not be so protected. in applications where externally radiated noise is minimal, it may be possible to reduce any screening to pins 1 and 16 and the diode connections only. screening may not be necessary in some instances, but this largely depends on the level of radiated noise, the decoupling/filtering employed and the receivers decoding technique. decoupling typical decoupling arrangements for use with or without the regulator are given in figs. 4 and 3, respectively. when using the regulator, further improvements in high frequency supply rejection are possible by the inclusion of r2. the value can be chosen so as to keep the pin 12 end of r2 within the 2 90 to 2 18v (wrt pin 7) specified voltage range. for example, if the SL486 is used in a system with a supply of 16v, a typical value tor r2 would be 200 w . note that the regulator is a low impedance point between pins 12 and 13. c7 thus maintains a low impedance path between pins 4 and 12 at high frequencies. application notes - refer to fig. 4 diode anode and cathode (pins 1 and 16) the infra-red receiving diode is connected between pins 1 and 16. the input circuit is configured so as to reject signals common to both pins. this improves the stability of the device, and greatly reduces the sensitivity to radiated electrical noise, the diode is reverse biased by a nominal 065v gyrator c2 and c1 (pins 2 and 3) the decoupling, provided by gyrator c2 and c1, rolls off the gain of the feedback loop which balances the dc component of the infra-red diode current. the values of c2 and c1 are chosen to produce a low frequency cut-off characteristic below a nominal 2khz. hence, the gyrator produces approximately 20db rejection at 100hz. the gyrator consists of two feedback loops operating in tandem. only one feedback path is functional when the dc component of the diode current is less than 200 m a. this loop is decoupled by gyrator c2. for diode currents between 200 m a and 15ma the second control loop is operative, and this is decoupled by gyrator c1. the decoupling capacitors, gyrator c2 and c1, must be connected between pins 2 and 3, to pin 4. the series imped- ance of c2 and c1 should be kept to a minimum. first stage decouple (pin 15) the capacitor on pin 15 decouples the signal from the non-inverting input of the first difference amplifier (see also fig. 2). the capacitance of 15nf is chosen to produce a 2khz low frequency roll-off. the capacitor must be connected between pins 15 and 14 (the input ground). second stage decouple (pin 5) the capacitor on pin 5 decouples the signal from the non-inverting input of the second difference amplifier. the capacifance of 33nf is chosen to produce a 2khz low frequency roll-off. the capaci- tor must be connected between pins 5 and 4 (the input v cc ). fourth stage decouple (pin 6) the capacitor on pin 6 decouples the signal from the non-inverting input of the fourth difference amplifier. the capacitance of 4.7nf is chosen to produce a 2khz low frequency roll-off. the capacitor must be connected between pins 6 and 7 (the output v cc ). agc decouple/delay adjust (pin 8) the output of the fourth difference amplifier is followed by a peak detector, which is used to provide an agc control level. this produces a current source which is limited to 10ma at pin 8. the agc decoupling capacitor (c5 normally 150nf) filters the pulsed input, and the resultant level controls the gain of the first three difference amplifiers. the agc control level exhibits a fast attack/slow decay characteristic. immediately infra-red pulses are detected, the gain will be reduced, so that any weaker noise pulses that are also received will not be seen at the output. thus, provided the infra-red pulses are the most intense, it is possible to receive data in noisy environments. the slow decay keeps the agc level intact during data reception, and produces a delay before any received noise may become present at the output, when transmission ceases. output (pin 9) the output will be low, pulsing high with a source impedance of a nominal 55k w , for a received infra- red pulse. it is a linear amplification of the input and swings between output ground and output v cc . stretch input and stretch output (pins 10 and 11) a typical infra-red ppm system transmits very narrow pulses. the duration of these pulses is typically 15 m s, so in order to use a microprocessor-based decoder system it is necessary to lengthen the received pulse. this stretched output can be obtained from pin 11 when a capacitor is connected between pins 9 and 10 (c8 in fig. 4). the width of the pulse is determined by the value of this coupling capacitor and is defined in the electrical character- istics. the stretch output is normally high, pulsing low for a received infra-red pulse and swings between v cco and v eeo . it must be noted that the stretch output logic sense is
4 SL486 c2 68 m c1 * 68 m c3 33n c4 47n i-r receiver diode c6 * 22 m c5 150n c9 15n 0v 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 SL486 c8 ? c10 * c7 * 033 m r1 * 50 r2 * output v cc ? see application notes * see operating notes 68 m 33n 47n i-r receiver diode 22 m 150n c9 15n 0v 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 SL486 output v cc can be omitted if already in application circuit fig. 3 circuit diagram of minimum component application (low voltage operation) fig. 4 SL486 application diagram showing all optional components (note: supply decoupling and connections for use of voltage regulator, also pulse stretch output) fig. 5 pcb track (actual size)and component layout for the circuit of fig. 4, using SL486 in dp16 package SL486 SL486 SL486 1 v cc 0v output r2 or wire link wire link, removed for use with regulator selectable output via wire link c8 (optional) i-r receiver diode c2 c1 c3 c4 c5 c7 c6 c9 r1 copper side component side
5 SL486 68 m 68 m 22n 47n 22 m 150n 15n 0v 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 SL486 033 m 50 200 ppm 16v system 1 16v fig. 6 SL486 application showing the use of the on-chip regulator fig. 7 microprocessor interface, using the SL486 pulse stretching facility 68 m 68 m 22n 47n 22 m 150n 15n 0v 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 SL486 033 m 50 stretched ppm microprocessor 1 5v c8 * * see text and electrical characteristics
6 SL486 package details dimensions are shown thus: mm (in) headquarters operations gec plessey semiconductors cheney manor, swindon, wiltshire sn2 2qw, united kingdom. tel: (0793) 518000 fax: (0793) 518411 gec plessey semiconductors p.o. box 660017 1500 green hills road, scotts valley, ca95067-0017 united states of america. tel (408) 438 2900 fax: (408) 438 5576 customer service centres l france & benelux les ulis cedex tel: (1) 64 46 23 45 fax : (1) 64 46 06 07 l germany munich tel: (089) 3609 06-0 fax : (089) 3609 06-55 l italy milan tel: (02) 66040867 fax: (02) 66040993 l japan tokyo tel: (3) 5276-5501 fax: (3) 5276-5510 l north america scotts valley, usa tel: (408) 438 2900 fax: (408) 438 7023. l south east asia singapore tel: (65) 3827708 fax: (65) 3828872 l sweden stockholm tel: 46 8 702 97 70 fax: 46 8 640 47 36 l uk, eire, denmark, finland & norway swindon tel: (0793) 518510 fax : (0793) 518582 these are supported by agents and distributors in major countries world-wide. ? gec plessey semiconductors 1994 publication no. ds3055 issue no. 2.2 april 195 this publication is issued to provide information only which (unless agreed by the company in writing) may not be used, applied or reproduced for any purpose nor form part of any order or contract nor to be regarded as a representation relating to the products or services concerned. no warranty or guarantee express or implied is made regard ing the capability, performance or suitability of any product or service. the company reserves the right to alter without prior knowledge the specification, design or price of any product or service. information concerning possible methods of use is provided as a guide only and does not constitute any guarantee that such methods of use will be satisfactory in a specific piece of equipment. it is the user's responsibility to fully determine the performance and suitability of any equipment using such information and to ensure that any publication or data used is up to date and has not been superseded. these products are not suitable for use in any medical products whose failure to perform may result in significant injury or death to the user. all products and materials are sold and services provided subject to the company's conditions of sale, w hich are available on request. 051 (002) min 16 leads at 254 (010) nom. spacing 038/061 (0015/024) 2032 (0800) max 711 (028) max 16-lead plastic dil C dp16 1 16 305 (0120) min pin 1 ref notch 023/041 (0009/0016) 762 (03) nom ctrs 508/(020) max 114/165 (0045/0065) notes 1. controlling dimensions are inches. 2. this package outline diagram is for guidance only. please contact your gps customer service centre for further information. seating plane 035/049 (0014/0019) 380/400 (0150/0157) 580/620 (0228/0244) 980/1001 (0386/0394) 16 16-lead miniature plastic dil - mp16 16 leads at 127 (0050) nom spacing 069 (0027) max 010/025 (0004/0010) 135/191 (0053/0075) spot ref. chamfer ref. 037 (0015) 3 45 019/025 (0007/0010) 0-8 041/127 (0016/0050) pin 1 notes 1. controlling dimensions are millimetres. 2. this package outline diagram is for guidance only. please contact your gps customer service centre for further information.
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